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NCP1597A 1 MHz, 2.0 A Synchronous Buck Regulator
The NCP1597A family are fixed 1 MHz, high-output-current, synchronous PWM converters that integrate a low-resistance, high-side P-channel MOSFET and a low-side N-channel MOSFET. The NCP1597A utilizes current mode control to provide fast transient response and excellent loop stability. It regulates input voltages from 4.0 V to 5.5 V down to an output voltage as low as 0.8 V and is able to supply up to 2.0 A. The NCP1597A includes an internally fixed switching frequency (FSW), and an internal soft-start to limit inrush currents. Using the EN pin, shutdown supply current is reduced to 3 mA maximum. Other features include cycle-by-cycle current limiting, short-circuit protection, power saving mode and thermal shutdown.
Features http://onsemi.com MARKING DIAGRAM
1 DFN6 CASE 506AH 1 1597A AYWWG G
* Input Voltage Range: from 4.0 V to 5.5 V * Internal 140 mW High-Side Switching P-Channel MOSFET and * * * * * * * * * * * * * * * * *
90 mW Low-Side N-Channel MOSFET Fixed 1 MHz Switching Frequency Cycle-by-Cycle Current Limiting Overtemperature Protection Internal Soft-Start Start-up with Pre-Biased Output Load Adjustable Output Voltage Down to 0.8 V Power Saving Mode During Light Load These are Pb-Free Devices DSP Power Hard Disk Drivers Computer Peripherals Home Audio Set-Top Boxes Networking Equipment LCD TV Wireless and DSL/Cable Modem USB Power Devices
A = Assembly Location Y = Year WW = Work Week G = Pb-Free Package (Note: Microdot may be in either location)
PIN CONNECTIONS
FB 1 GND 2 LX 3 6 EN 5 VCC 4 VCCP
ORDERING INFORMATION
Device NCP1597AMNTWG Package DFN6 (Pb-Free) Shipping 3000 / Tape & Reel
Applications
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.
(c) Semiconductor Components Industries, LLC, 2010
June, 2010 - Rev. 0
1
Publication Order Number: NCP1597/D
NCP1597A
BLOCK DIAGRAM
NCP1597A VCCP VCC Power Reset UVLO THD Hiccup + CA -
NC/EN
+
OSC
Soft-Start
PMOS M1
Vref FB
+ + gm -
- PWM +
Control Logic
LX
GND
Figure 1. Block Diagram PIN DESCRIPTIONS
Pin No 1 2 3 4 5 6 EP Symbol FB GND LX VCCP VCC EN PAD Description Feedback input pin of the Error Amplifier. Connect a resistor divider from the converter's output voltage to this pin to set the converter's output voltage. Ground pin. Connect to thermal pad. The drains of the internal MOSFETs. The output inductor should be connected to this pin. Power input for the power stage Input supply pin for internal bias circuitry. A 0.1 mF ceramic bypass capacitor is preferred to connect to this pin. Logic input to enable the part. Logic high to turn on the part and logic low to shut off the part. Exposed pad of the package provides both electrical contact to the ground and good thermal contact to the PCB. This pad must be soldered to the PCB for proper operation.
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NCP1597A
APPLICATION CIRCUIT
Vin 4.0 V - 5.5 V
VCCP VCC NC/EN
LX GND FB
Vout
Figure 2. NCP1597A
ABSOLUTE MAXIMUM RATINGS
Rating Power Supply Pin (Pin 4, 5) to GND Symbol Vin Value 6.5 -0.3 (DC) -1.0 (t < 100 ns) Vin + 0.3 -0.6 (DC) -1.0 (t < 100 ns) 6.0 -0.3 (DC) -1.0 (t < 100 ns) TA TJ TS RqJA -40 to +85 -40 to +150 -55 to +150 68.5 Unit V
LX to GND
V
All other pins
V
Operating Temperature Range Junction Temperature Storage Temperature Range Thermal Resistance Junction-to-Air (Note 1)
C C C C/W
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. 1. RqJA measured on approximately 1x1 inch sq. of 1 oz. Copper.
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NCP1597A
ELECTRICAL CHARACTERISTICS
(Vin = 4.0 V - 5.5 V, Vout = 1.2 V, TJ = +25C for typical value; -40C < TJ < 85C for min/max values unless noted otherwise) Parameter Vin Input Voltage Range VCC UVLO Threshold UVLO Hysteresis VCC Quiescent Current VCCP Quiescent Current Vin Shutdown Supply Current (Note 2) FEEDBACK VOLTAGE Reference Voltage Feedback Input Bias Current Feedback Voltage Line Regulation PWM Maximum Duty Cycle (Regulating) Minimum Controllable ON Time (Note 2) PULSE-BY-PULSE CURRENT LIMIT Pulse-by-Pulse Current Limit (Regulation) Pulse-by-Pulse Current Limit (Soft-Start) OSCILLATOR Oscillator Frequency MOSFET High Side MOSFET ON Resistance High Side MOSFET Leakage (Note 2) Low Side MOSFET ON Resistance Low Side MOSFET Leakage (Note 2) ENABLE (NCP1597A) EN HI Threshold EN LO Threshold EN Hysteresis EN Pullup Current SOFT-START Soft-Start Ramp Time Hiccup Timer THERMAL SHUTDOWN Thermal Shutdown Threshold Thermal Shutdown Hysteresis 2. Guaranteed by design. Not production tested. 185 30 C C tSS FSW = 1 MHz 1.0 2.0 ms ms ENHI ENLO 200 1.4 3.0 1.4 0.4 V V mV mA RDS(on) HS RDS(on) LS IDS = 100 mA, VGS = 5 V VEN = 0 V, VSW = 0 V IDS = 100 mA, VGS = 5 V VEN = 0 V, VSW = 5 V 90 140 200 10 125 10 mW mA mW mA FSW 0.87 1.0 1.13 MHz ILIM ILIMSS 2.7 4.0 3.9 5.3 4.3 6.1 A A 83 85 50 % ns Vref IFB VFB = 0.8 V Vin = 4.0 V to 5.5 V 0.788 0.800 10 0.06 0.812 100 V nA %/V IinVCC IinVCCP IQSHDN Vin = 5 V,VFB = 1.5 V, (No Switching) Vin = 5 V,VFB = 1.5 V, (No Switching) EN = 0 V Symbol Vin Test Conditions Min 4.0 3.2 3.5 275 1.7 25 1.8 3.0 2.0 Typ Max 5.5 3.8 Unit V V mV mA mA mA
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NCP1597A
TYPICAL OPERATING CHARACTERISTICS
3.7 3.6 3.5 UVLO (V) 3.4 3.3 UVLO Falling Threshold 3.2 3.1 -40 UVLO Rising Threshold VFB, FB INPUT THRESHOLD (V) 85 815 810 805 800 795 790 785 -40
-15
10
35
60
-15
10
35
60
85
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
Figure 3. Undervoltage Lockout vs. Temperature
1.3 fSW, SWITCH FREQUENCY (MHz) 1.2 1.1 1.0 0.9 0.8 0.7 -40 6.0 5.5 5.0 4.5 4.0 3.5 -40
Figure 4. Feedback Input Threshold vs. Temperature
ILIM, CURRENT LIMIT (A)
ILIM (Soft-Start)
ILIM (Regulation)
-15
10
35
60
85
-15
10
35
60
85
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
Figure 5. Switching Frequency vs. Temperature
2.0 1.8 ICC, SWITCHING (mA) 1.6 1.4 1.2 1.0 -40 ICC, DISABLED (mA) 2.0 1.8 1.6 1.4 1.2 1.0 -40
Figure 6. Current Limit vs. Temperature
-15
10
35
60
85
-15
10
35
60
85
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
Figure 7. Quiescent Current Into VCC vs. Temperature
Figure 8. Quiescent Current Into VCC vs. Temperature
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NCP1597A
TYPICAL OPERATING CHARACTERISTICS
3.40 VOUT, OUTPUT VOLTAGE (V) 3.38 3.36 3.34 3.32 3.30 3.28 3.26 3.24 3.22 3.20 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VIN = 4.0 V VIN = 5.0 V VOUT = 3.3 V L = 3.3 mH COUT = 2 x 22 mF EFFICIENCY (%) 100 90 80 70 60 50 40 30 20 0.01 0.1 VOUT = 3.3 V L = 3.3 mH COUT = 2 x 22 mF 1 10 IOUT, OUTPUT CURRENT (A) VIN = 4.0 V VIN = 5.0 V
IOUT, OUTPUT CURRENT (A)
Figure 9. Load Regulation for VOUT = 3.3 V
Figure 10. Efficiency vs. Output Current for VOUT = 3.3 V
100
1.90 VOUT, OUTPUT VOLTAGE (V) 1.88 1.86 1.84 1.82 1.80 1.78 1.76 1.74 1.72 1.70 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VOUT = 1.8 V L = 3.3 mH COUT = 2 x 22 mF EFFICIENCY (%)
90 80 VIN = 5.0 V VIN = 4.0 V 70 60 50 40 30 20 0.01
VIN = 4.0 V VIN = 5.0 V
VOUT = 1.8 V L = 3.3 mH COUT = 2 x 22 mF 0.1 1 10
IOUT, OUTPUT CURRENT (A)
IOUT, OUTPUT CURRENT (A)
Figure 11. Load Regulation for VOUT = 1.8 V
Figure 12. Efficiency vs. Output Current for VOUT = 1.8 V
100
1.30 VOUT, OUTPUT VOLTAGE (V) 1.28 1.26 1.24 1.22 1.20 1.18 1.16 1.14 1.12 1.10 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VIN = 4.0 V VOUT = 1.2 V L = 3.3 mH COUT = 2 x 22 mF EFFICIENCY (%) VIN = 5.0 V
90 80 70 60 50 40 30 20 0.01
VIN = 4.0 V VIN = 5.0 V
VOUT = 1.2 V L = 3.3 mH COUT = 2 x 22 mF 0.1 1 10 IOUT, OUTPUT CURRENT (A)
IOUT, OUTPUT CURRENT (A)
Figure 13. Load Regulation for VOUT = 1.2 V
Figure 14. Efficiency vs. Output Current for VOUT = 1.2 V
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NCP1597A
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: LX Pin Switching Waveform, 2 V/div Middle Trace: Output Ripple Voltage, 20 mV/div Lower Trace: Inductor Current, 1 A/div
(VIN = 5 V, ILOAD = 700 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: LX Pin Switching Waveform, 2 V/div Middle Trace: Output Ripple Voltage, 20 mV/div Lower Trace: Inductor Current, 1 A/div
Figure 15. DCM Switching Waveform for VOUT = 3.3 V
Figure 16. CCM Switching Waveform for VOUT = 3.3 V
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: LX Pin Switching Waveform, 2 V/div Middle Trace: Output Ripple Voltage, 20 mV/div Lower Trace: Inductor Current, 200 mA/div
(VIN = 5 V, ILOAD = 400 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: LX Pin Switching Waveform, 2 V/div Middle Trace: Output Ripple Voltage, 20 mV/div Lower Trace: Inductor Current, 1 A/div
Figure 17. DCM Switching Waveform for VOUT = 1.2 V
Figure 18. CCM Switching Waveform for VOUT = 1.2 V
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: EN Pin Voltage, 2 V/div Middle Trace: Output Voltage, 1 V/div Lower Trace: Inductor Current, 100 mA/div
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: EN Pin Voltage, 2 V/div Middle Trace: Output Voltage, 1 V/div Lower Trace: Inductor Current, 100 mA/div
Figure 19. Soft-Start Waveforms for VOUT = 3.3 V
Figure 20. Soft-Start Waveforms for VOUT = 1.2 V
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NCP1597A
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: Output Dynamic Voltage, 100 mV/div Lower Trace: Output Current, 500 mA/div
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 mH, COUT = 2 x 22 mF) Upper Trace: Output Dynamic Voltage, 100 mV/div Lower Trace: Output Current, 500 mA/div
Figure 21. Transient Response for VOUT = 3.3 V
Figure 22. Transient Response for VOUT = 3.3 V
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 H, COUT = 2 x 22 mF) Upper Trace: Output Dynamic Voltage, 100 mV/div Lower Trace: Input Current, 500 mA/div
(VIN = 5 V, ILOAD = 100 mA, L = 3.3 H, COUT = 2 x 22 mF) Upper Trace: Output Dynamic Voltage, 100 mV/div Lower Trace: Input Current, 500 mA/div
Figure 23. Transient Response for VOUT = 1.2 V
Figure 24. Transient Response for VOUT = 1.2 V
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NCP1597A
DETAILED DESCRIPTION
Overview
The NCP1597A is a synchronous PWM controller that incorporates all the control and protection circuitry necessary to satisfy a wide range of applications. The NCP1597A employs current mode control to provide fast transient response, simple compensation, and excellent stability. The features of the NCP1597A include a precision reference, fixed 1 MHz switching frequency, a transconductance error amplifier, an integrated high-side P-channel MOSFET and low-side N-Channel MOSFET, internal soft-start, and very low shutdown current. The protection features of the NCP1597A include internal soft-start, pulse-by-pulse current limit, and thermal shutdown.
Reference Voltage
delivering up to 2.0 A of current. When the controller is disabled or during a Fault condition, the controller's output stage is tri-stated by turning OFF both the upper and lower MOSFETs.
Adaptive Dead Time Gate Driver
The NCP1597A incorporates an internal reference that allows output voltages as low as 0.8 V. The tolerance of the internal reference is guaranteed over the entire operating temperature range of the controller. The reference voltage is trimmed using a test configuration that accounts for error amplifier offset and bias currents.
Oscillator Frequency
In a synchronous buck converter, a certain dead time is required between the low side drive signal and high side drive signal to avoid shoot through. During the dead time, the body diode of the low side FET freewheels the current. The body diode has much higher voltage drop than that of the MOSFET, which reduces the efficiency significantly. The longer the body diode conducts, the lower the efficiency. In NCP1597A, the drivers and MOSFETs are integrated in a single chip. The parasitic inductance is minimized. Adaptive dead time control method is used in NCP1597A to prevent the shoot through from happening and minimizing the diode conduction loss at the same time.
Pulse Width Modulation
A fixed precision oscillator is provided. The oscillator frequency range is 1 MHz with $13% variation.
Transconductance Error Amplifier
The transconductance error amplifier's primary function is to regulate the converter's output voltage using a resistor divider connected from the converter's output to the FB pin of the controller, as shown in the applications Schematic. If a Fault occurs, the amplifier's output is immediately pulled to GND and PWM switching is inhibited.
Internal Soft-Start
A high-speed PWM comparator, capable of pulse widths as low as 50 ns, is included in the NCP1597A. The inverting input of the comparator is connected to the output of the error amplifier. The non-inverting input is connected to the the current sense signal. At the beginning of each PWM cycle, the CLK signal sets the PWM flip-flop and the upper MOSFET is turned ON. When the current sense signal rises above the error amplifier's voltage then the comparator will reset the PWM flip-flop and the upper MOSFET will be turned OFF.
Power Save Mode
To limit the startup inrush current, an internal soft start circuit is used to ramp up the reference voltage from 0 V to its final value linearly. The internal soft start time is 1 ms typically.
Output MOSFETs
If the load current decreases, the converter will enter power save mode operation automatically. During power save mode, the converter skips switching and operates with reduced frequency, which minimizes the quiescent current and maintain high efficiency.
Current Sense
The NCP1597A includes low RDS(on), both high-side P-channel and low-side N-channel MOSFETs capable of
The NCP1597A monitors the current in the upper MOSFET. The current signal is required by the PWM comparator and the pulse-by-pulse current limiter.
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NCP1597A
PROTECTIONS
Undervoltage Lockout (UVLO)
The under voltage lockout feature prevents the controller from switching when the input voltage is too low to power the internal power supplies and reference. Hysteresis must be incorporated in the UVLO comparator to prevent IxR drops in the wiring or PCB traces from causing ON/OFF cycling of the controller during heavy loading at power up or power down.
Overcurrent Protection (OCP)
overcurrent detection while charging the output capacitors. Hiccup mode reduces input supply current and power dissipation during a short circuit. It also allows for much improved system up-time, allowing auto-restart upon removal of a temporary short-circuit.
Pre-Bias Startup
NCP1597A detects high side switch current and then compares to a voltage level representing the overcurrent threshold limit. If the current through the high side FET exceeds the overcurrent threshold limit for seven consecutive switching cycles, overcurrent protection is triggered. Once the overcurrent protection occurs, hiccup mode engages. First, hiccup mode, turns off both FETs and discharges the internal compensation network at the output of the OTA. Next, the IC waits typically 2 ms and then resets the overcurrent counter. After this reset, the circuit attempts another normal soft-start. During soft-start, the overcurrent protection threshold is increased to prevent false
In some applications the controller will be required to start switching when it's output capacitors are charged anywhere from slightly above 0 V to just below the regulation voltage. This situation occurs for a number of reasons: the converter's output capacitors may have residual charge on them or the converter's output may be held up by a low current standby power supply. NCP1597A supports pre-bias start up by holding Low side FETs off till soft start ramp reaches the FB Pin voltage.
Thermal Shutdown
The NCP1597A protects itself from over heating with an internal thermal monitoring circuit. If the junction temperature exceeds the thermal shutdown threshold both the upper and lower MOSFETs will be shut OFF.
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NCP1597A
APPLICATION INFORMATION
Programming the Output Voltage
The output voltage is set using a resistive voltage divider from the output voltage to FB pin (see Figure 25). So the output voltage is calculated according to Eq.1.
V out + V FB @
Vout
C OUT(min) +
I ripple 8 @ f @ V ripple
(eq. 3)
R1 ) R2 R2
(eq. 1)
Where Vripple is the allowed output voltage ripple. The required ESR for this amount of ripple can be calculated by equation 5.
ESR + V ripple I ripple
(eq. 4)
R1
FB R2
Based on Equation 2 to choose capacitor and check its ESR according to Equation 3. If ESR exceeds the value from Eq.4, multiple capacitors should be used in parallel. Ceramic capacitor can be used in most of the applications. In addition, both surface mount tantalum and through-hole aluminum electrolytic capacitors can be used as well.
Maximum Output Capacitor
Figure 25. Output divider Inductor Selection
NCP1597A family has internal 1 ms fixed soft-start and overcurrent limit. It limits the maximum allowed output capacitor to startup successfully. The maximum allowed output capacitor can be determined by the equation:
C out(max) + I lim(min) * I load(max) * V out T SS(min)
Di p-p 2
The inductor is the key component in the switching regulator. The selection of inductor involves trade-offs among size, cost and efficiency. The inductor value is selected according to the equation 2.
L+ V out f @ I ripple @ 1* V out V in(max)
(eq. 2)
(eq. 5)
Where Vout - the output voltage; f - switching frequency, 1.0 MHz; Iripple - Ripple current, usually it's 20% - 30% of output current; Vin(max) - maximum input voltage. Choose a standard value close to the calculated value to maintain a maximum ripple current within 30% of the maximum load current. If the ripple current exceeds this 30% limit, the next larger value should be selected. The inductor's RMS current rating must be greater than the maximum load current and its saturation current should be about 30% higher. For robust operation in fault conditions (start-up or short circuit), the saturation current should be high enough. To keep the efficiency high, the series resistance (DCR) should be less than 0.1 W, and the core material should be intended for high frequency applications.
Output Capacitor Selection
Where TSS(min) is the minimum soft-start period (1ms); DiPP is the current ripple. This is assuming that a constant load is connected. For example, with 3.3 V/2.0 A output and 20% ripple, the max allowed output capacitors is 546 mF.
Input Capacitor Selection
The input capacitor can be calculated by Equation 6.
C in(min) + I out(max) @ D max @ 1 f @ V in(ripple)
(eq. 6)
Where Vin(ripple) is the required input ripple voltage.
D max + V out V in(min) is the maximum duty cycle.
(eq. 7)
Power Dissipation
The output capacitor acts to smooth the dc output voltage and also provides energy storage. So the major parameter necessary to define the output capacitor is the maximum allowed output voltage ripple of the converter. This ripple is related to capacitance and the ESR. The minimum capacitance required for a certain output ripple can be calculated by Equation 4.
The NCP1597A is available in a thermally enhanced 6-pin, DFN package. When the die temperature reaches +185C, the NCP1597A shuts down (see the Thermal-Overload Protection section). The power dissipated in the device is the sum of the power dissipated from supply current (PQ), power dissipated due to switching the internal power MOSFET (PSW), and the power dissipated due to the RMS current through the internal power MOSFET (PON). The total power dissipated in the package must be limited so the junction temperature does not exceed its absolute maximum rating of +150C at
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NCP1597A
maximum ambient temperature. Calculate the power lost in the NCP1597A using the following equations: 1. High side MOSFET The conduction loss in the top switch is:
P HSON + I
2 RMS_HSFET
T J + T C ) P TOTAL @ q JC
(eq. 15)
R DS(on)HS
(eq. 8)
Where:
I RMS_FET + I out 2 ) DI PP 12
2
D
(eq. 9)
qJC is the junction-to-case thermal resistance equal to 1.7C/W. TC is the temperature of the case and TJ is the junction temperature, or die temperature. The case-to-ambient thermal resistance is dependent on how well heat can be transferred from the PC board to the air. Solder the underside-exposed pad to a large copper GND plane. If the die temperature reaches the thermal shutdown threshold the NCP1597A shut down and does not restart again until the die temperature cools by 30C.
Layout Consideration
DIPP is the peak-to-peak inductor current ripple. The power lost due to switching the internal power high side MOSFET is:
P HSSW + V in @ I out @ t r ) t f @ f SW 2
(eq. 10)
tr and tf are the rise and fall times of the internal power MOSFET measured at SW node. 2. Low side MOSFET The power dissipated in the top switch is:
P LSON + I RMS_LSFET 2 @ R DS(on)LS
(eq. 11)
Where:
I RMS_LSFET + I out 2 ) DI PP 12
2
@ (1 * D )
(eq. 12)
DIPP is the peak-to-peak inductor current ripple. The switching loss for the low side MOSFET can be ignored. The power lost due to the quiescent current (IQ) of the device is:
P Q + V in @ I Q P TOTAL + P HSON ) P HSSW ) P LSON ) P Q
(eq. 13)
IQ is the switching quiescent current of the NCP1597A.
(eq. 14)
Calculate the temperature rise of the die using the following equation:
As with all high frequency switchers, when considering layout, care must be taken in order to achieve optimal electrical, thermal and noise performance. For 1.0MHz switching frequency, switch rise and fall times are typically in few nanosecond range. To prevent noise both radiated and conducted the high speed switching current path must be kept as short as possible. Shortening the current path will also reduce the parasitic trace inductance of approximately 25 nH/inch. At switch off, this parasitic inductance produces a flyback spike across the NCP1597A switch. When operating at higher currents and input voltages, with poor layout, this spike can generate voltages across the NCP1597A that may exceed its absolute maximum rating. A ground plane should always be used under the switcher circuitry to prevent interplane coupling and overall noise. The FB component should be kept as far away as possible from the switch node. The ground for these components should be separated from the switch current path. Failure to do so will result in poor stability or subharmonic like oscillation. Board layout also has a significant effect on thermal resistance. Reducing the thermal resistance from ground pin and exposed pad onto the board will reduce die temperature and increase the power capability of the NCP1597A. This is achieved by providing as much copper area as possible around the exposed pad. Adding multiple thermal vias under and around this pad to an internal ground plane will also help. Similar treatment to the inductor pads will reduce any additional heating effects.
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NCP1597A
PACKAGE DIMENSIONS
DFN6 3x3, 0.95P CASE 506AH-01 ISSUE O
D A B
NOTES: 1. DIMENSIONS AND TOLERANCING PER ASME Y14.5M, 1994. 2. CONTROLLING DIMENSION: MILLIMETERS. 3. DIMESNION b APPLIES TO PLATED TERMINAL AND IS MEASURED BETWEEN 0.25 AND 0.30 MM FROM TERMINAL. 4. COPLANARITY APPLIES TO THE EXPOSED PAD AS WELL AS THE TERMINALS. MILLIMETERS MIN NOM MAX 0.80 0.90 1.00 0.00 0.03 0.05 0.20 REF 0.35 0.40 0.45 3.00 BSC 2.40 2.50 2.60 3.00 BSC 1.50 1.60 1.70 0.95 BSC 0.21 --- --- 0.30 0.40 0.50
PIN 1 REFERENCE
E
2X
0.15 C
2X
0.15 C 0.10 C
6X
0.08 C SIDE VIEW
6X
L
1
6X
K
6 4
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone: 303-675-2175 or 800-344-3860 Toll Free USA/Canada Fax: 303-675-2176 or 800-344-3867 Toll Free USA/Canada Email: orderlit@onsemi.com N. American Technical Support: 800-282-9855 Toll Free USA/Canada Europe, Middle East and Africa Technical Support: Phone: 421 33 790 2910 Japan Customer Focus Center Phone: 81-3-5773-3850 ON Semiconductor Website: www.onsemi.com Order Literature: http://www.onsemi.com/orderlit For additional information, please contact your local Sales Representative
CCC CCC CCC
D2
TOP VIEW
A (A3) A1 e
3 4X
C
SEATING PLANE
DIM A A1 A3 b D D2 E E2 e K L
SOLDERING FOOTPRINT*
0.450 0.0177 0.950 0.0374
E2 3.31 0.130
6X
1.700 0.685
b
(NOTE 3)
0.10 C A B BOTTOM VIEW 0.05 C 0.63 0.025 2.60 0.1023
SCALE 10:1 mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
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NCP1597/D

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